Feedbacks for low emittance accelerators

Slides:



Advertisements
Similar presentations
© 2003 Xilinx, Inc. All Rights Reserved Course Wrap Up DSP Design Flow.
Advertisements

FILTERS Presented by: Mohammed Alani Supervised By: Dr. Nazila Safavi
PEP II Transverse Feedback System Ron Akre Anatoly Krasnykh Uli Wienands MAC April 15, 2004.
1 Dr. Un-ki Yang Particle Physics Group or Shuster 5.15 Amplifiers and Feedback: 3.
Quantization Prof. Siripong Potisuk.
Digital Signal Processing Techniques ECE2799 Lecture Prof. W. Michalson.
EECS 20 Chapter 9 Part 21 Convolution, Impulse Response, Filters Last time we Revisited the impulse function and impulse response Defined the impulse (Dirac.
Renesas Electronics America Inc. © 2012 Renesas Electronics America Inc. All rights reserved. Increase the Dynamic Range and Precision of Digital Filters.
STRIPLINE KICKER STATUS. PRESENTATION OUTLINE 1.Design of a stripline kicker for beam injection in DAFNE storage rings. 2.HV tests and RF measurements.
Filters and Delta Sigma Converters
Digital Signal Processing and Generation for a DC Current Transformer for Particle Accelerators Silvia Zorzetti.
Initial Performance Results of the APS P0 (Transverse Bunch-to-Bunch) Feedback System N. DiMonte#, C.-Y. Yao, Argonne National Laboratory, Argonne, IL.
January 19, 2006PEP TFB R.Akre PEP II Transverse Feedback System Ron Akre William Colocho Anatoly Krasnykh Vojtech Pacak Dmitry Teytelman Uli Wienands.
Digital Phase Control System for SSRF LINAC C.X. Yin, D.K. Liu, L.Y. Yu SINAP, China
Frank Ludwig, DESY Content : 1 Stability requirements for phase and amplitude for the XFEL 2 Next LLRF system for optimized detector operation 3 Limitations.
Digital Phase Control System for SSRF LINAC C.X. Yin, D.K. Liu, L.Y. Yu SINAP, China
Bavarian Forest, Bavarian Forest, 24 April 2009 D. Alberto Signal Processing for Nuclear Detectors, Bavarian Forest, 24 April 2009 Dipartimento di Fisica.
Quiz 1 Review. Analog Synthesis Overview Sound is created by controlling electrical current within synthesizer, and amplifying result. Basic components:
Fast feedback, studies and possible collaborations Alessandro Drago INFN-LNF ILCDR07 Damping Rings R&D Meeting 5-7 March 2007.
Bunch by bunch feedback systems for KEKB Makoto Tobiyama KEK Accelerator Laboratory.
R.SREEDHARAN  SOLEIL main parameters  Booster and storage ring low level RF system  New digital Booster LLRF system under development  Digital LLRF.
GROUP MEMBERS ELISHBA KHALID 07-CP-07 TAHIRA SAMEEN 07-CP-31.
Experience and Perspectives of Transverse Feedback Systems for Scrubbing Thanks to: SPS OP crew and colleagues from BE-ABP and BE-RF, for their support.
IoP HEPP/APP annual meeting 2010 Feedback on Nanosecond Timescales: maintaining luminosity at future linear colliders Ben Constance John Adams Institute,
LFB, LLRF, TFB Alessandro Drago Annecy, March 2010.
Feedback Simulations with Amplifier Saturation, Transient and Realistic Filtering Mauro Pivi, Claudio Rivetta, Kevin Li Webex CERN/SLAC/LBNL 13 September.
Real-time Digital Signal Processing Digital Filters.
Beam Secondary Shower Acquisition System: RF design techniques for 40MHz ADC Student Meeting Jose Luis Sirvent PhD. Student 30/09/2013.
Bunch by bunch feedback systems for KEKB Makoto Tobiyama KEK Accelerator Laboratory.
Feedback System Design Alessandro Drago SuperB Meeting January 2000 SLAC.
Application of digital filter in engineering
LFB, LLRF, TFB update Alessandro Drago XIII SuperB General Meeting Isola d’Elba, 5/30-6/
Multi-bunch Feedback System Review and Challenges for 1-2GHz Japan Synchrotron Radiation Research Institute (JASRI) SPring-8 T. Nakamura CFA Beam Dynamics.
Feedback Systems Update Alessandro Drago SuperB General Meeting Perugia June 2009.
Enhancement Presentation Carlos Abellan Barcelona September, 9th 2009.
Superfast BPM Processor Scheme Stephen Molloy, QMUL Nano-Project Mini-Workshop at ATF.
MECH 373 Instrumentation and Measurements
Introduction to Discrete-Time Control Systems fall
PEP II Transverse Feedback System
Digital Control CSE 421.
Dither Luminosity feedback versus Fast IP feedback
Glen White, SLAC Jan th ATF2 Project Meeting, KEK
Bunch-by-bunch feedbacks and Low Level RF
Digital transmission over a fading channel
B.Sc. Thesis by Çağrı Gürleyük
Lattice Struture.
Working groups status report on Feedbacks
COMPUTER ORGANIZATION & ASSEMBLY LANGUAGE
Adaptive Filters Common filter design methods assume that the characteristics of the signal remain constant in time. However, when the signal characteristics.
Horizontal e+ instability Study & Solution
S-D analog to digital conversion
P. Forck, P. Kowina, M. Schwickert, R. Singh
Design of Digital Filter Bank and General Purpose Digital Shaper
Calorimeter Upgrade Meeting
Front-end electronic system for large area photomultipliers readout
Digital Control Systems Waseem Gulsher
Upgrading the Digital Component of the Bunch Current Monitors
لجنة الهندسة الكهربائية
Intrabunch feedback system development at DAFNE
Intra-Pulse Beam-Beam Scans at the NLC IP
Everything You Ever Wanted to Know About Filters*
Lesson 8: Analog Signal Conversion
A Software Defined Radio for the Masses, Part 4
Digital Control Systems Waseem Gulsher
Chapter 6 Discrete-Time System
The performance requirements for DSP applications continue to grow and the traditional solutions do not adequately address this new challenge Paradigm.
Analog-to-digital converter
Feedback Systems in Circular Colliders
Undulator Cavity BPM System Status
Breakout Session SC3 – Undulator
Presentation transcript:

Feedbacks for low emittance accelerators Alessandro Drago SuperB Meeting   30 May 2008 - 04 June 2008 La Biodola, Isola d'Elba Italy

Introduction This talk wants to discuss the question: “There is anything to do to make bunch-by-bunch feedback system compatible with low (or very low) emittance accelerators?” In my opinion the answer is YES

The starting point The starting point for a discussion about how to upgrade bunch-by-bunch feedback, in this talk is taken from two digital system designs, both originated at SLAC: I) the GBoard system proposed in the 2002/2003 by J.D.Fox and D.Teytelman and still to be implemented II) the iGp system, the engineerized version of the Gboard prototype (Gproto), implemented at DAFNE, KEK, PEP-II, ALS, Duke Univ. Note: nowadays, due to the advance of the FPGA technology, there are no more reasons to have different digital feedback design for transverse and longitudinal systems (as in PEP-II, DAFNE, KEK)

Proposed at the ICFA’03 Workshop at Alghero by J.D.Fox & D.Teytelman

Considering R&D feedback for low emittance accelerators The R&D list for an upgrade starting from iGp-like system (in the software & gateware version running at the present at DAFNE) includes: very low noise analog front end @ 3*RF maintain low cross-talk between adjacent bunches under 40 dB (better 60 dB) dual separated timing to pilot the backend power stage digital block with higher dynamic range (12/16bits) “dual gain” approach to minimize residual beam motion integrated beam-feedback model

Considering a feedback upgrade for low emittance accelerators Feedback are active system and can have strong negative impact on very low emittance beams The basic ideas of the upgrades consist in making the noise in the feedback loop as low as possible, and this means: a) Filtering at the best the external noise, i.e. coming or generated outside the feedback b) Reducing the internal noise, i.e. the noise coming from parts in the feedback system c) Reduce the crosstalk between bunch signals

1) Very low noise analog front end @ 3*RF From the rings, at revolution frequency o lower, the beam signal is much more noisy than at higher frequencies. To solve this trouble, it is possible to built a very low noise front end at 3 or 4 times RF to acquire a much more “clean” beam signal

Noise from pickup @ low frequencies (no beam!)

Longitudinal “conceptual” FE used @ PEP-II & DAFNE

ALS LFB new front end Courtesy of D.Teytelman

PEP II Transverse Feedback System The PEP TFB system takes the vector sum of 2 BPMs, delays the signal by the remainder of 1 turn and delivers a kick to the beam the next time around. Two stripline kickers, one for X and one for Y, are used. [MAC 10/26/2006 – Ron Akre ]

PEP II TFB Receiver 10/26/2006 – Ron Akre PHASE TRANSIENT Use These Phase Shifters to Remove Phase Transient PHASE TRANSIENT

1) Very low noise analog front end @ 3*RF It would be an important point to design a very low noise n*RF analog front end studying new generation components : (amplifiers, mixers, phase shifters,…) It is necessary to make tests and measurements in laboratory and on real beam signals

2) Maintain low cross-talk between adjacent bunches < 40 dB (better <60 dB) This is very important for ultra-low emittance rings but it is an important issue in general The crosstalk is a source of noise For example in DAFNE the vertical feedback crosstalk estimate is ~30 dB, probably this value is to high for low emittance beams Actions: to be evaluated

3) Separated digital timing to pilot backend power stage and kickers Typically a transverse kicker has two ports In the PEP-II scheme (seen previously) it is used a fine digital step delay for each port In DAFNE there is only a common delay for the 2 kicker ports; it is put inside the iGp to control the clock to DAC This is a much better approach because it doesn’t insert jitter in the feedback loop, it doesn’t limit the bandwidth nor attenuate the correction signal The timing control should be duplicated to delay the clock before the fast output DAC A solution is to double the fast DAC in the iGp output stage to control separately positive and negative output signal

4) Digital block with higher dynamic range (12/16bits) ? The iGp (as well the GBoard) feedback samples the input beam signal by an 8 bits analog to digital converter Do we need more bits conversion? In my opinion the answer is yes Because a small bits A-to-D conversion gives poor voltage resolution and bigger quantization noise Because the dynamic range could be not sufficient

Resuming the dynamic range in DAFNE transverse Feedback Analog Front end (AM143) dynamic range = 79.50 dB (measured) Analog Back end (ZFL500LN) dynamic range = 77.97 dB (measured) Power Amplifier (AR250250) dynamic range = 87.83 dB (measured) Digital Part (8 bits ADC) dynamic range = 48.16 dB (computed) Digital Part (7.5 bits ADC) dynamic range = 45.15 dB (computed) Note on the used formula: dyn_range = 20*log10 (Vout_max/Vout_min) in dB [if analog system] dyn_range = 20*log10 (2^adc_num_of_bit) in dB [if digital system]

The dynamic range in DAFNE feedback analog blocks is in the range 78 dB – 88 dB

ADC dynamic range versus # of bits 7.5_bit ADC_= 45.15 dB 8_bit ADC _ = 48.16 dB 10_bit ADC _= 60.20 dB 12_bit ADC _= 72.25 dB 14_bit ADC _= 84.29 dB [best value considering the analog blocks!] 15_bit ADC _= 90.31 dB 16_bit ADC = 96.33 dB 24_bit ADC = 144.49 dB Note: in general at least 0.5 bit (= 3dB) is not effective in the conversion

A factor liming the effectiveness of the ADC is the sampling clock jitter. I can suppose that a realistic value of the RMS jitter for the timing signal will be ~0.5 ps [Need to know the SuperB timing specifications] In this case (yellow trace), the ADC dynamic range should be better than 60 dB (12bits)

Recommendation on dynamic range A reasonable compromise between the present electronics technology and the specifications seems to indicate these choices: 12 bits (eventually 14 bits) for analog-to-digital conversion 16 bits for digital-to-analog conversion

5) “Dual gain” approach to minimize residual beam motion To minimize the feedback impact on a low emittance beam, the feedback gain should be held as low as possible to minimize the unfiltered residual beam motion passing through the system During injection or if necessary to control instabilities, the feedback needs all the power while in a “stable” situation the system probably needs much less gain It could be interesting to implement a “Dual gain” approach, but how it should be done?

In the digital part , the FE_signal_out is sampled by an A/D converter at rf frequency, and then demultiplexed to separate the signal of each bunch. A digital signal processor (DSP) farm is used to implement a passband filter [finite impulse response (FIR) or infinite impulse response (IIR). The number of taps, gain with sign, center frequency, filter shape, and phase response are programmable by the users.

IIR and FIR bandpass filter for each bunch For every bunch the correction signal is function only of previous input (FIR) Or the previous input / output (if IIR) values

To have a “dual gain” feedback a new FIR formula could be tested y(n,k)=G*[b(n,k) *x(n,k) +b(n-1,k) *x(n-1,k) +...+b(n-j,k) *x(n-j,k) + + b(n,k-1) *x(n,k-1) +b(n-1,k-1) *x(n-1,k-1) +...+b(n-j,k-1) *x(n-j,k-1) + + b(n,k-2) *x(n,k-2) +b(n-1,k-2) *x(n-1,k-2) +...+b(n-j,k-2) *x(n-j,k-2) + . +b(n,k-h-1)*x(n,k-h-1)+b(n-1,k-h-1)*x(n-1,k-h-1)+...+b(n-j,k-h-1)*x(n-j,k-h-1)] y = output correction value, x = input value, b = constant coefficient n = discrete time (turn), k = selected bunch, j=filter taps, h= harmonic number In the above formula, the outputs of k bunch are function not only of the k bunch previous values but also of inputs from the other bunches. In case of injection or instability the gain will rise up very fast.

“Dual gain” FIR formula analysis The first row is exactly what we use now First row coefficients can be find experimentally In the first approximation, the coefficient for the other bunches could be put at zero The other rows coefficient should be find by using a beam-feedback model with MATLAB/SIMULINK simulator In the second approximation only the first column coefficient should be identified

“Dual gain” feedback by a second FIR formula (to be tested) y(n,k) = G* [ b(n,k)*x(n,k) + b(n-1,k)*x(n-1,k) + . . . +b(n-j,k) *x(n-j,k) ] G is a dynamic function of the other bunch signals for example a simple formula can be used: G= g *{max[ x(n,k-1), x(n,k-2), .....x(n-j,k-h-1)]} g is gain from operator interface y = output correction value, x = input value, b = constant coefficient n = discrete time (turn), k = selected bunch, j=filter taps, h= harmonic number In the above formula, the outputs of k bunch are function of the k bunch previous values but the gain of the feedback depends by the inputs of the other bunches. In case of injection or instability, the gain will rise up very fast.

What do we need to implement the new FIR formulae ? Much powerful hardware A beam-feedback model to compute and manage the coefficients and test the filter behavior

2001 VIRTEX-II

Xilinx Virtex-5 performances

6) Integrated beam-feedback model In the past a beam/feedback model has been used by Teytelman & Fox to implement IIR filter, because it was the only way to find its coefficient too difficult to find experimentally To implement the “Dual Gain” FIR formula is also necessary to use a model/simulator to find the coefficients of the formula Nowadays much more powerful commercial software tools make very interesting synergy between model and real system

D. Teytelman, et al., “Design and implementation of IIR algorithms for control of longitudinal coupled-bunch instabilities” , BIW 2000, SLAC-PUB-8411, May 2000 Example of MATLAB/SIMULINK Beam/feedback model to compute IIR filter coefficients for only one bunch

Using MATLAB and SIMULINK, the real time code can be easier integrated with the simulator code !

Conclusions It is necessary to prove the effectiveness of the 6 proposed points DAFNE is a perfect test machine because has low harmonic number, low RF frequency and low number of bunches so tests on the proposal 4), 5) and 6) can be implemented easier than in other accelerators To start the experimentations we need time, a running accelerator, manpower and money !