EECS 465: Digital Systems Lecture Notes # 2

Slides:



Advertisements
Similar presentations
K-Map Simplification COE 202 Digital Logic Design Dr. Aiman El-Maleh
Advertisements

Based on slides by: Charles Kime & Thomas Kaminski © 2004 Pearson Education, Inc. ECE/CS 352: Digital System Fundamentals Lecture 8 – Systematic Simplification.
1 Combinational Logic Network design Chapter 4 (continued ….)
ECE C03 Lecture 21 Lecture 2 Two Level Minimization Hai Zhou ECE 303 Advanced Digital Design Spring 2002.
ECEN 248: INTRODUCTION TO DIGITAL SYSTEMS DESIGN Lecture 6 Dr. Shi Dept. of Electrical and Computer Engineering.
Gate-Level Minimization. Digital Circuits The Map Method The complexity of the digital logic gates the complexity of the algebraic expression.
Chapter 3 Simplification of Switching Functions
CSCE 211: Digital Logic Design Chin-Tser Huang University of South Carolina.
Give qualifications of instructors: DAP
Computer Engineering (Logic Circuits) (Karnaugh Map)
Introduction Gate-level minimization refers to the design task of finding an optimal gate-level implementation of Boolean functions describing a digital.
بهينه سازي با نقشة کارنو Karnaugh Map. 2  Method of graphically representing the truth table that helps visualize adjacencies 2-variable K-map 3-variable.
EECC341 - Shaaban #1 Lec # 7 Winter Combinational Circuit Minimization Canonical sum and product logic expressions do not provide a circuit.
Simplifying Boolean Expressions Using K-Map Method
Overview Part 2 – Circuit Optimization 2-4 Two-Level Optimization
Chapter 2: Boolean Algebra and Logic Functions
Lecture 3: Incompletely Specified Functions and K Maps CSE 140: Components and Design Techniques for Digital Systems Fall 2014 CK Cheng Dept. of Computer.
BOOLEAN ALGEBRA Saras M. Srivastava PGT (Computer Science)
1 Simplification of Boolean Functions:  An implementation of a Boolean Function requires the use of logic gates.  A smaller number of gates, with each.
1 Chapter 5 Karnaugh Maps Mei Yang ECG Logic Design 1.
Chapter 3 Simplification of Switching Functions. Simplification Goals Goal -- minimize the cost of realizing a switching function Cost measures and other.
Chapter 3 The Karnaugh Map. These K-maps are described by the location. Next, each square will be 1 or 0 depending on the value of the function. ABfm.
Department of Computer Engineering
CHAPTER 1 INTRODUCTION TO DIGITAL LOGIC. K-Map (1)  Karnaugh Mapping is used to minimize the number of logic gates that are required in a digital circuit.
Optimization Algorithm
Examples. Examples (1/11)  Example #1: f(A,B,C,D) =  m(2,3,4,5,7,8,10,13,15) Fill in the 1’s. 1 1 C A B CD AB D 1 1.
UM EECS 270 Spring 2011 – Taken from Dr.Karem Sakallah Logic Synthesis: From Specs to Circuits Implementation Styles –Random –Regular Optimization Criteria.
Converting to Minterms Form
Computer Engineering (Logic Circuits) (Karnaugh Map)
Chapter3: Gate-Level Minimization Part 1 Origionally By Reham S. Al-Majed Imam Muhammad Bin Saud University.
CHAPTER 3: PRINCIPLES OF COMBINATIONAL LOGIC
Ahmad Almulhem, KFUPM 2010 COE 202: Digital Logic Design Combinational Logic Part 3 Dr. Ahmad Almulhem ahmadsm AT kfupm Phone: Office:
CHAPTER 1 INTRODUCTION TO DIGITAL LOGIC
1 Example: Groupings on 3-Variable K-Maps BC F(A,B,C) = A ’ B ’ A BC F(A,B,C) = B ’ A
 Seattle Pacific University EE Logic System DesignKMaps-1 Two-Level Simplification All Boolean expressions can be represented in two- level forms.
CSE 140: Components and Design Techniques for Digital Systems Lecture 3: Incompletely Specified Functions and K Maps CK Cheng Dept. of Computer Science.
Digital Logic (Karnaugh Map). Karnaugh Maps Karnaugh maps (K-maps) are graphical representations of boolean functions. One map cell corresponds to a row.
CMPUT Computer Organization and Architecture II1 CMPUT329 - Fall 2003 Topic 4: Cost of Logic Circuits and Karnaugh Maps José Nelson Amaral.
Karnaugh Maps (K maps).
CEC 220 Digital Circuit Design More Karnaugh Maps Monday, February 02 CEC 220 Digital Circuit Design Slide 1 of 11.
ECE 301 – Digital Electronics Minimizing Boolean Expressions using K-maps, The Minimal Cover, and Incompletely Specified Boolean Functions (Lecture #6)
Chapter 3 Simplification of Switching Functions. Simplification Goals Goal -- minimize the cost of realizing a switching function Cost measures and other.
1 CS 352 Introduction to Logic Design Lecture 4 Ahmed Ezzat Multi-level Gate Circuits and Combinational Circuit Design Ch-7 + Ch-8.
1 EENG 2710 Chapter 3 Simplification of Switching Functions.
CHAPTER 1 INTRODUCTION TO DIGITAL LOGIC:K-Map. K-Map (1)  Karnaugh Map provides a systematic method for simplifying Boolean expressions and may produce.
CHAPTER 3 Simplification of Boolean Functions
Computer Organisation
EECS 465: Digital Systems Design Lecture Notes #3
CS 352 Introduction to Logic Design
CSCE 211: Digital Logic Design
Optimized Implementation of Logic Function
CSCE 211: Digital Logic Design
EECS 465: Digital Systems Lecture Notes # 2
Optimized Implementation of Logic Function
CSCE 211: Digital Logic Design
CSCE 211: Digital Logic Design
CSCE 211: Digital Logic Design
ECE 331 – Digital System Design
EECS 465: Digital Systems Lecture Notes # 2
CH7 Multilevel Gate Network
Optimization Algorithm
Chapter 3 Gate-level Minimization.
EECS 465: Digital Systems Design Lecture Notes #3
Optimized Implementation of Logic Function
CSCE 211: Digital Logic Design
COE 202: Digital Logic Design Combinational Logic Part 3
Overview Part 2 – Circuit Optimization
3-Variable K-map AB/C AB/C A’B’ A’B AB AB’
CSCE 211: Digital Logic Design
ECE 331 – Digital System Design
Presentation transcript:

EECS 465: Digital Systems Lecture Notes # 2 Two-Level Minimization Using Karnaugh Maps SHANTANU DUTT Department of Electrical & Computer Engineering University of Illinois, Chicago Phone: (312) 355-1314: e-mail: dutt@ece.uic.edu URL: http://www.ece.uic.edu/~dutt

Concepts in 2-Level Minimization Defn: An implicant g of a function is a product term (e.g., g=xyz) s.t. when g=1  f=1 Defn: A minterm is an implicant whose product term representation consists of all n variables of an n-var. function (each in either compl.or uncompl. form) Defn: Let g, and h be 2 implicants of a function f. g is said to cover h if h=1  g=1 (e.g., g = xz, h = xyz) Defn: Let G = {g1, .., gk} be a set of implicants of func f, and let h be another implicant of f. Then G is covers h if h=1  g1+ .. + gk =1 (generalized covering). Defn: An SOP or POS expression is also called a 2-level expression Defn: A 2-level AND-OR (OR-AND) gate realization of an SOP (POS) expression is one in which all product terms (OR terms in POS) in the SOP (POS) expression are implemented by multiple input AND (OR) gates & the ORing (ANDing) of the product (OR) terms is realized by a multiple input OR (AND) gate.

3 A AB + BC + ACD B f1 B C A C Level 2 D Level 1 B (B + C)(A + D)(C + D) C f2 A D C D

3 E.g. f1 = AB + BC + ACD --- 2-level. (SOP) f2 = ( B+C )( A+D )( C+D ) --- 2-level (POS) f3 =AB + AC( B+D ) --- not SOP or POS level 1 I/Ps --- not 2-level --- 3 level ( can be realized directly by 3 levels of gates) A B A f3 C B level 2 I/Ps D level 2 gates level 3 gate level 0 I/Ps level 1 gates

5 Defn. A gate in a logic circuit is a level-1 gate if all its inputs are primary inputs (i.e., literals, A, A, B, B, etc.) A gate is a level-i gate i > 1 if the highest-level gate whose output feeds the (level-i) gate is a level-(i-1) gate. NOTE: If a given expr. is not 2-level, we can convert it to a 2-level one using the distributive law. The goal of 2-level minimization is to minimize the number of literals (a literal is a var. in complemented or uncompl. form) in a 2-level logic expr.. This approx. reduces the total # of inputs over all level-1 gates (AND gates in an SOP expr. , OR gates in a POS expr.) in the circuit in a 2-level gate realization.

E.g. f = ABC + ABC + ABC (non-minimized 9 literals) A B (12 gate I/Ps) 6 E.g. f = ABC + ABC + ABC (non-minimized 9 literals) A B (12 gate I/Ps) = Circuit complexity C A f B C A B C f = AB + AC (minimized 4 literals) A f B (6 gate I/Ps) = Circuit complexity A C Note: Minimizing # of literals + # of product terms  minimizing total # of gate inputs in a 2-level impl.  approx. min. total # of gate i/ps of a multi-level impl. (reqd. when gates of certain sizes reqd. by the minimized expression is not available)

Multilevel Minimization (Example): 7 Multilevel Minimization (Example): f = x1x2x3 + x2x3x4 + x1x5 + x4x5 (2-level minimized) Apply distributive law (factoring) f = x2x3(x1 + x4) + x5(x1 + x4) = (x2x3 + x5)(x1 + x4) -- Multilevel expr. Cost = 14 (# of gate i/ps in a 2-level impl.) Cost = 8 (# of gate i/ps). Can increase delay though due to more levels of gates & more interconnects that the critical path has to go through Simple gate delay model: prop. to # of inputs Gate Impl.: x2 x3 x5 x1 x4 f Multilevel circuit Critical path goes through 3 2-i/p gates (6 units of delay) and 2 interconns. (not counting i/p and o/p interconnects). The critical path in a 2-level impl. of the above SOP expr. will go through a total of 7 gate units of delay but only 1 interconnect.

8 Defn. Two implicants (or product terms) of a function f are said to be adjacent (logically) if they have the same literals except in one variable xi which occurs in uncomplemented form (xi) in one implicant and in complemented form (xi) in the other. The 2 implicants are said to differ in xi. E.g. ABC, ABC (adjacent implicants, differ in B) ABD, ABC (not adjacent) NOTE: Adjacent implicants can be combined into one implicant by the combining theorem (ABC + ABC = AC)

Another ordering of inputs ( Gray-code ordering) A B Z1 0 0 0 0 1 1 9 Karnaugh Maps 2-variable TT outputs A B Z1 Z2 Binary place-value ordering (Binary ordering) 0 0 0 0 Physically adjacent but not logically adjacent. 0 1 1 1 1 0 0 1 1 1 1 0 logically adjacent but not physically adjacent AB + AB B Another ordering of inputs ( Gray-code ordering) A B Z1 0 0 0 0 1 1 1 1 1 1 0 0 Z1 = B Physically as well as logically adjacent.

n-variable Gray-code ordering 10 n-variable Gray-code ordering Defn. Gi = i-bit Gray-code ordering rev(Gi) = reverse order of Gi Gn = 0 Gn-1 1 rev(Gn-1) G1 = 0 Base. 1 G2 = 0 G1 1 rev(G1) 0 0 0 1 1 1 1 0 A B C 0 0 0 0 0 1 0 1 1 0 1 0 1 1 0 1 1 1 1 0 1 1 0 0 = G3 = 0 G2 1 rev(G2) = Convert to a 2-dimensional Gray-code ordered TT AB x 110 C 00 01 11 10 y 1 Throw away variable (A) changing across the 2 squares. We thus obtain BC. 1 1 001

11 Example ( 3-var. K-Map) Consensus = BC Function f: AB C 00 01 11 10 1 1 1 1 1 1 f = AB + AB + AC + BC Consensus = BC A’B’ AC’ B’C’ Gray code ordering Note: 1) that the consensus theorem is an example of generalized covering discussed earlier. 2) AC’ is also a consensus, this time of AB and B’C’. Can’t discard both simultaneously! Need to apply gen. covering (incl. consensus) one at a time. Defn. A Prime Implicant (PI) of a function f is an implicant of f that is not covered by any other implicant of f. Defn. An Essential PI is a PI that covers/includes at least one minterm that is not covered by any other PI. Four PIs AB, BC, AC, AB formed. Not all these PIs are needed in the expression. Only a minimum set that covers all minterms is needed. In the above example, AB & AB are essential PIs. These will need to be present in any SOP expr. of the function. To form a minimal set, the PI BC can be used. Thus f = AB + AB + BC is a minimized expression.

Larger than 2-minterm PIs can also exist: E.g., 12 Larger than 2-minterm PIs can also exist: AB AB E.g., C 00 01 11 10 C 00 01 11 10 1 1 1 1 1 1 1 1 AB AB B C B 2-minterm implicants (AB, AB in the 1st example above) can be merged if they are logically adjacent to form a 4-minterm implicant and so on.

When an implicant can not be “grown” any further, then it is a PI. 13 When an implicant can not be “grown” any further, then it is a PI. Defn. In a K-map, 2 implicants can be logically adjacent if they are symmetric, i.e., if : (1) They are disjoint (no common minterms). (2) They cover the same # of minterms. (3) Each minterm in one implicant is adjacent to a unique minterm in the other implicant. AB More Examples: Both PIs (A, BC) are essential. C 00 01 11 10 AB Redrawn 1 C 00 01 11 10 1 1 1 1 1 1 1 1 1 1 1 Not symmetric Thus, f = A + BC is minimized. Symmetric ( logically adjacent) 2-minterm implicants : Can be “merged” to form a 4-minterm implicant, which will be a PI.

14 4-variable K-Map: Gray code ordering AB CD Gray code ordering 00 01 11 10 00 01 Gray code ordering 11 10

Instead of starting with 2-minterm implicants & growing them, you 15 Example: f = AC + D Instead of starting with 2-minterm implicants & growing them, you can form larger implicants directly by grouping power of 2 (2, 4, 8, etc.) # of minterms so as to form a rectangle or square ( a convex region). AB CD 00 01 11 10 00 1 1 1 1 1 1 01 AC 11 10 1 1 1 1 Convex D Concave AB CD 00 01 11 10 Invalid grouping (region formed is concave) f = AB + AC + BCD 00 01 11 10 1 1 1 1 Valid groupings 1 1 1 1

16 Another Example: AB CD BD ABD C f = C + BD + ABD TT: 00 01 11 10 00 01 11 10 A B C D Z 0 0 0 0 1 0 0 0 1 0 0 0 1 0 1 0 0 1 1 1 0 1 0 0 0 0 1 0 1 1 0 1 1 0 1 0 1 1 1 1 1 0 0 0 1 1 0 0 1 0 1 0 1 0 1 1 0 1 1 1 1 1 0 0 0 1 1 0 1 0 1 1 1 0 1 1 1 1 1 1 00 01 1 1 ABD 1 C 11 10 1 1 1 1 Binary order 1 1 1 1 f = C + BD + ABD

Many times certain input combinations are invalid for a function 17 Don’t Cares in K-Maps Many times certain input combinations are invalid for a function (E.g. BCD to 7-segment display functions; see pp. 212-214 in Katz text ) For such combinations, we do not care what the output is, and we put an ‘x’ in the o/p column for the TT AB CD 00 01 11 10 A B C f 0 0 0 1 0 0 1 0 0 1 0 1 0 1 1 x 1 0 0 0 1 0 1 1 1 1 0 x 1 1 1 x 1 x x 1 0 0 1 1 0 f = BC + AB by considering all x’s as 0s f = B The x’s can, however, be profitably used to make larger PIs & thus further simplify the function. by selectively considering the 010 cell’s x as 1

In a K-map, the ‘x’s can be profitably used to form larger implicants (which have fewer literals) 18 However, when we need to form a minimal PI cover, we need to worry only about covering the minterms ( the 1s), and not the Xs. • Thus as far as x’s are concerned, we can have the cake and eat it too! Example: f(A,B,C,D) = m(1,3,5,7,9) + d(2,6,12,13) AB CD 00 01 11 10 00 01 11 10 0 4 12 x 8 1 1 5 1 13 x 9 1 3 1 7 1 15 11 2 x 6 x 14 10 LSBs MSBs AC AD A B C D 0 0 0 0 0 0 0 1 0 0 1 0 0 0 1 1 f = CD + AD or CD + AC If input comb. 2,6 occur o/p is 0. If inputs 2,6 occur o/p = 1. Which to use for lower dynamic power (consumed on a 0  1 transition at the o/p)?

STEPS IN K-MAP MINIMIZATION (sop EXPR.) 19 STEPS IN K-MAP MINIMIZATION (sop EXPR.) STEP1: Form all PIs by including the Xs with the 1s to form larger PIs. (Do not form PIs covering only Xs !) STEP2: Identify all essential PIs by visiting each minterm (1s) & checking if it is covered by only one PI. If so, then that PI is an essential PI. STEP3: Identify all 1s not covered by essential PIs. Select a minimal- cost set of PIs S to cover them. This requires some trial-and error (in fact, this is a hard computational problem). STEP4: Minimal SOP Expr. for function f: f = essential PIs + Pi Pi S PI Pi is in set S

Minimal POS Expr. from a K-Map : 20 METHOD 1: Obtain minimal SOP expression for the complement function f, and complement this SOP expression to get a minimal POS expr. for f (using De-Morgan’s Law) Big M notation Example: F (A,B,C,D) = M(0,2,4,8,10,11,14,15) D(6,12,13) Xs of F 0s of F AB F F AB CD CD 00 01 11 10 D 0 0 x 0 1 1 x 1 00 01 11 10 1 1 x 1 0 0 x 0 0 0 1 1 1 x 1 1 00 01 11 10 Complement 0 4 12 8 1 5 13 9 3 1 7 1 15 0 11 0 2 0 6 x 14 0 10 0 AC F =D + AC F = D + AC = D(A +C)

Example: (Method2: Direct Method) 21 Example: (Method2: Direct Method) AB (OR terms) CD 00 01 11 10 0 0 x 0 1 1 x 1 1 1 0 0 0 x 0 0 00 01 11 10 Prime Implicate ( Groups of 0s that cannot be grown any further) Both D and A + C are Essential Prime Implicates. D (A + C) F = D( A + C ) ( Product of Prime Implicates )

METHOD2 : Direct Method : 22 (1) Obtain all prime implicates (PTs) (largest groups of 0s & Xs of size 2 , i 0, forming a convex region, that can not be “grown” any further). (2) Identify all essential PTs (those that cover at least one 0 not covered by any other PT). (3) Choose a minimal set T of PTs to cover the 0s not covered by the set of essential PTs. (4) The expression for a PT is an OR term obtained by discarding all changing variables, & keeping variables complemented if they are constant at 1 or uncomplemented if they are constant at 0 & taking the OR (sum) of these literals. (5) Minimal POS Expr.: f = (essential PTs) qi qi T

5-variable K-map: f(A,B,C,D,E): Juxtapose two 4-var. K-submaps 23 5-variable K-map: f(A,B,C,D,E): Juxtapose two 4-var. K-submaps one for the MSB A=0 and the other for A=1: BC BC 00 01 11 10 DE DE 00 01 11 10 00 01 11 10 00 01 11 10 0 4 12 8 1 5 13 9 3 7 15 11 2 6 14 10 16 20 28 24 17 21 29 25 19 23 31 27 18 22 30 26 A=0 A=1 4-var. K-submap 4-var. K-submap Adjacencies of a square: Adjacent squares of the 4-var. K-submap plus the “corresponding” or “mirror” square in the other 4-var. K-submap. Example: BC BC DE 00 01 11 10 DE 00 01 11 10 00 01 11 10 00 01 11 10 16 20 28 x 24 17 21 29 1 25 19 x 23 1 31 x 27 18 22 1 30 1 26 0 1 4 12 1 8 1 5 13 1 9 3 1 7 1 15 x 11 2 6 14 x 10 A=0 A=1

6-variable K-map: f(A,B,C,D,E,F)--Juxtapose two 5-var. K-submaps 24 6-variable K-map: f(A,B,C,D,E,F)--Juxtapose two 5-var. K-submaps one for the MSB A=0 and other for A=1 CD CD EF 00 01 11 10 EF 00 01 11 10 00 01 11 10 00 01 11 10 0 4 12 8 1 5 13 9 3 7 15 11 2 6 14 10 16 20 28 24 17 21 29 25 19 23 31 27 18 22 30 26 5-var. K-submap A=0 B=0 B=1 CD CD EF 00 01 11 10 00 01 11 10 EF 00 01 11 10 00 01 11 10 32 36 44 40 33 37 45 41 35 39 47 43 34 38 46 42 48 52 60 56 49 53 61 57 51 55 63 59 50 54 62 58 5-var. K-submap A=1 B=1 B=0 Adjacencies of a square: Adjacent squares of the 5-var. K-submap plus the “corresponding” or “mirror” square in the other 5-var. K-submap.

6-variable K-map: f(A,B,C,D,E,F,)---Example: 25 6-variable K-map: f(A,B,C,D,E,F,)---Example: CD CD EF 00 01 11 10 EF 00 01 11 10 00 01 11 10 00 01 11 10 0 4 12 8 1 5 13 9 3 7 15 11 2 6 14 10 16 20 28 24 17 21 29 25 19 23 31 27 18 22 30 26 A=0 B=0 B=1 CD CD EF 00 01 11 10 00 01 11 10 EF 00 01 11 10 00 01 11 10 32 36 44 40 33 37 45 41 35 39 47 43 34 38 46 42 48 52 60 56 49 53 61 57 51 55 63 59 50 54 62 58 A=1 B=1 B=0